Bandlimiting

Bandlimiting refers to a process which reduces the energy of a signal to an acceptably low level outside of a desired frequency range.

Bandlimiting is an essential part of many applications in signal processing and communications. Examples include controlling interference between radio frequency communications signals, and managing aliasing distortion associated with sampling for digital signal processing.



Bandlimited signals
A bandlimited signal is, strictly speaking, a signal with zero energy outside of a defined frequency range. In practice, a signal is considered bandlimited if its energy outside of a frequency range is low enough to be considered negligible in a given application.

A bandlimited signal may be either random (stochastic) or non-random (deterministic).

In general, infinitely many terms are required in a continuous Fourier series representation of a signal, but if a finite number of Fourier series terms can be calculated from that signal, that signal is considered to be band-limited. In mathematic terminology, a bandlimited signal has a Fourier transform or spectral density with bounded support.

Sampling bandlimited signals
A bandlimited signal can be fully reconstructed from its samples, provided that the sampling rate exceeds twice the bandwidth of the signal. This minimum sampling rate is called the Nyquist rate associated with the Nyquist–Shannon sampling theorem.

Real world signals are not strictly bandlimited, and signals of interest typically have unwanted energy outside of the band of interest. Because of this, sampling functions and digital signal processing functions which change sample rates usually require bandlimiting filters to control the amount of aliasing distortion. Bandlimiting filters should be designed carefully to manage other distortions because they alter the signal of interest in both its frequency domain magnitude and phase, and its time domain properties.

An example of a simple deterministic bandlimited signal is a sinusoid of the form $$x(t) = \sin(2 \pi ft + \theta). $$ If this signal is sampled at a rate $$f_s =\tfrac{1}{T} > 2f $$ so that we have the samples $$x(nT), $$ for all integers $$n$$, we can recover $$x(t) $$ completely from these samples. Similarly, sums of sinusoids with different frequencies and phases are also bandlimited to the highest of their frequencies.

The signal whose Fourier transform is shown in the figure is also bandlimited. Suppose $$x(t) $$ is a signal whose Fourier transform is $$X(f), $$ the magnitude of which is shown in the figure. The highest frequency component in $$x(t) $$ is $$B. $$ As a result, the Nyquist rate is


 * $$ R_N = 2B \, $$

or twice the highest frequency component in the signal, as shown in the figure. According to the sampling theorem, it is possible to reconstruct $$x(t)\ $$ completely and exactly using the samples


 * $$x(nT) = x \left( { n \over f_s } \right)  $$ for all integers $$n \, $$ and $$T \ \stackrel{\mathrm{def}}{=}\  { 1 \over f_s } $$

as long as


 * $$f_s > R_N \, $$

The reconstruction of a signal from its samples can be accomplished using the Whittaker–Shannon interpolation formula.

Bandlimited versus timelimited
A bandlimited signal cannot be also timelimited. More precisely, a function and its Fourier transform cannot both have finite support unless it is identically zero. This fact can be proved using complex analysis and properties of the Fourier transform.

Proof: Assume that a signal f(t) which has finite support in both domains and is not identically zero exists. Let's sample it faster than the Nyquist frequency, and compute respective Fourier transform $$ FT(f) = F_1(w) $$ and discrete-time Fourier transform $$ DTFT(f) = F_2(w)$$. According to properties of DTFT, $$ F_2(w) = \sum_{n=-\infty}^{+\infty} F_1(w+n f_x) $$, where $$f_x$$ is the frequency used for discretization. If f is bandlimited, $$ F_1 $$ is zero outside of a certain interval, so with large enough $$ f_x $$, $$ F_2 $$ will be zero in some intervals too, since individual supports of $$ F_1 $$ in sum of $$ F_2 $$ won't overlap. According to DTFT definition, $$ F_2 $$ is a sum of trigonometric functions, and since f(t) is time-limited, this sum will be finite, so $$ F_2 $$ will be actually a trigonometric polynomial. All trigonometric polynomials are holomorphic on a whole complex plane, and there is a simple theorem in complex analysis that says that all zeros of non-constant holomorphic function are isolated. But this contradicts our earlier finding that $$ F_2 $$ has intervals full of zeros, because points in such intervals are not isolated. Thus the only time- and bandwidth-limited signal is a constant zero.

One important consequence of this result is that it is impossible to generate a truly bandlimited signal in any real-world situation, because a bandlimited signal would require infinite time to transmit. All real-world signals are, by necessity, timelimited, which means that they cannot be bandlimited. Nevertheless, the concept of a bandlimited signal is a useful idealization for theoretical and analytical purposes. Furthermore, it is possible to approximate a bandlimited signal to any arbitrary level of accuracy desired.

A similar relationship between duration in time and bandwidth in frequency also forms the mathematical basis for the uncertainty principle in quantum mechanics. In that setting, the "width" of the time domain and frequency domain functions are evaluated with a variance-like measure. Quantitatively, the uncertainty principle imposes the following condition on any real waveform:


 * $$ W_B T_D \ge 1 $$

where


 * $$W_B$$ is a (suitably chosen) measure of bandwidth (in hertz), and


 * $$T_D$$ is a (suitably chosen) measure of time duration (in seconds).

In time–frequency analysis, these limits are known as the Gabor limit, and are interpreted as a limit on the simultaneous time–frequency resolution one may achieve.